Protection circuit for a cathode ray tube

ABSTRACT

A circuit for protecting a cathode ray tube screen from damage by an electron beam includes a semiconductor switch device having an input coupled to a signal related to a deflection signal for the electron beam. The switch device is coupled to a voltage supply and the circuit further includes a charge storage device coupled to the switch device and further coupled to a control grid of the cathode ray tube. The charge storage device is charged through the switch device by the voltage supply when the deflection signal is present at a control input of the switch device. The switch device decouples the supply voltage from the charge storage device when the deflection signal is not present and places a negative blanking voltage developed on the charge storage device across the control grid when the deflection signal is not present to cut-off beam current in the cathode ray tube.

This invention relates to video display apparatus, and in particular, to projection-type video display apparatus having multiple cathode ray tubes and, even more particularly, to cathode ray tube (CRT) protection circuits operating in response to deflection loss.

Projection video display apparatus, such as television receivers, normally include three monochrome cathode ray tubes individually producing red, green and blue images. A magnifying lens assembly typically is mounted to each of the cathode ray tubes and transmits light from the tubes to one or more mirrors where the light is reflected onto a viewing area of a projection screen, for rear projection-type receivers. The screen transmits some of the light so that an enlarged image formed from the superimposed images from each of the cathode ray tubes is viewable from a position in front of the screen. The screen acts to diffuse the light from the tubes somewhat to increase the audience viewing angle in order to enlarge the acceptable viewing region about the front of the screen.

In order to form a final enlarged image of sufficient brightness that viewing is acceptable under normal room lighting, it is necessary that the individual cathode ray tube be operated at high brightness levels, corresponding to high levels of electron beam current density. Loss or reduction of horizontal or vertical deflection or scan of any or all of the cathode ray tube electron beams will cause an undesirable concentration of electron beam energy over a small region of the phosphor display screen of one or more of the cathode ray tubes. This may cause permanent damage to the display screen if the scan loss or reduction condition persists for even a short time, and particularly when horizontal scan loss occurs and a vertical line or spot (no vertical or horizontal deflection) appears on the CRT screen. It is therefore important that some form of protection circuit be provided that quickly senses a loss or reduction of electron beam deflection and responds in an appropriate manner, such as by blanking the electron beam or beams, to prevent damage to the cathode ray tubes.

U.S. Pat. No. 4,642,532 to Hoover discloses a projection TV deflection loss protection circuit wherein signals representative of vertical and horizontal deflection currents are sensed. In the event of a loss of either of the horizontal or vertical deflection signal, a signal is generated to disable the kine driver circuits and therefore to blank out the CRT screen.

It may be desirable to provide a protection circuit which will protect the CRT screen from phosphor burn when deflection loss occurs even when one or more of the video drive circuits or amplifiers short, for example a collector to emitter short, in which case the CRT cathode may be very close to ground level and to the grid voltage.

It may also be desirable to provide a protection circuit which provides for maximum video signal range, i.e., which allows the CRT grid to be at a voltage level sufficiently near the cathode potential to provide, in accordance with the video signal, a maximum beam current that can be produced by the CRT, but which also allows immediate CRT blanking should a sweep loss occur.

It may also be desirable to provide a CRT protection circuit which requires minimal active components such as transistors.

Another desirable feature of such a protection circuit may be to provide a minimal drain on the voltage supply for the cathode of the CRT immediately after the power supply is turned off.

It may be desirable to provide a CRT protection circuit which offers redundant CRT protection should a horizontal sweep-loss occur.

It may be desirable to provide a CRT protection circuit which is not required to be energized by any additional DC, low voltage power supplies other than the supply voltage for the cathode of the CRT of the television receiver.

It may be desirable to provide such a CRT protection circuit which keeps the CRT screen blanked for a substantial period of time following receiver turn off and which is quickly ready to blank out the CRT screen should scan loss occur, even immediately after the television receiver is turned on.

In accordance with an aspect of the invention, a circuit for protecting a cathode ray tube screen from damage by an electron beam emitted by the cathode of the tube is provided comprising switch means having a control input adapted to be coupled to a source of a signal related to a deflection signal for the electron beam, the switch means further being coupled to a voltage supply and further comprising a charge storage means coupled to the switch means and further coupled to a control grid of the cathode ray tube, the charge storage means being charged through a current that flows in the switch means from the voltage supply when the deflection signal is present at the control input of the switch means, the switch means decoupling the supply voltage from the charge storage means when the deflection signal is not present and placing a blanking voltage developed on the charge storage means across the control grid when the signal related to a deflection signal is not present to cut-off electron beam current in the cathode ray tube.

In an embodiment of the invention, the switch means comprises a PNP bipolar transistor and the signal representing a deflection signal comprises a signal representing the horizontal deflection signal of the television receiver. The blanking voltage comprises a negative voltage developed across the charge storage means, with the charge storage means comprising a capacitor.

FIGS. 1a and 1b illustrate a block and schematic diagram of a portion of a projection-type video display apparatus incorporating a protection circuit embodying aspects of the invention.

Referring to the FIGS. 1a and 1b, a projection-type video display apparatus, such as a television receiver, incorporates three monochrome CRT's or kinescopes 10, 11 and 12. Kinescope 10 illustratively produces red images, kinescope 11 produces green images, and kinescope 12 produces blue images. The three images are combined by an optical system onto a viewing screen to be displayed to the user.

Vertical deflection windings 14, 15 and 16 that are coupled between terminals RV--RV', GV--GV' and BV--BV', respectively, are coupled in series between an output terminal 13a of a vertical deflection circuit 13 and a terminal 13b. A DC blocking capacitor C_(V) and a current sampling resistor RS are coupled in series with windings 14, 15 and 16, between terminal 13a and ground. Circuit 13 produces a sawtooth vertical deflection current i_(v) that flows in capacitor C_(V) to produce a vertical rate signal VERT at terminal 13b that includes a parabolic voltage component during normal operation. Should a vertical scan loss occur, for example, when any one of windings 14, 15 and 16 is an open circuit, parabolic signal VERT will not be generated.

A line rate, or horizontal deflection circuit 122 generates horizontal drive signals at terminal RH--RH', GH--GH' and BH--BH', which are applied to and product horizontal deflection currents in horizontal deflection windings 20, 21 and 22, respectively. Horizontal deflection circuit 122 is coupled to a primary winding 121 of a flyback or high voltage transformer 11. High voltage transformer 11 includes a load circuit supply winding 31 which, via a diode D3 of a rectifying stage, produces a voltage level +V₁ at a terminal 32. Voltage level +V₁ may illustratively be of the order of +225 volts. Voltage level +V₁ is DC-coupled to the cathodes of CRT's 10, 11 and 12, as described later on.

During the trace interval of a deflection cycle, a trace voltage V₃₁ is developed across winding 31 of flyback transformer 11, in a well known manner. Trace voltage V₃₁ is, for example, -28 volts. A diode D2 that is poled to be conductive during trace is coupled between a terminal 31b of winding 31 and a common conductor or ground. Diode D2 couples trace voltage V₃₁ across a filter capacitor C5 for developing a positive voltage level +V₂ across capacitor C5 at a terminal 31a of winding 31 that energizes vertical deflection circuit 13. Voltage level +V₂ is approximately +26 volts.

High voltage transformer 11 also includes a winding 42 for developing a retrace pulse signal HOR at the horizontal line rate during normal operation of horizontal deflection circuit 122. Should a horizontal deflection loss occur, it is assumed that signal HOR will not be generated.

The high voltage transformer 11 also includes a winding 43 for producing the high voltage or ultor voltage for the cathode ray tube anode. Diode D1 is provided to rectify the ultor voltage. The ultor voltage is also typically provided to a focus anode of the CRT via a voltage divider circuit, not shown, for focus control and also may be provided to the CRT screen grids via a divider.

Vertical parabola signal VERT is AC coupled via capacitor C7 to a cathode of a diode D5 of a fault detector 70. Diode D5 has an anode that is coupled to a DC voltage V_(REF). Consequently, a parabolic voltage VERT1 that is clamped approximately to the level of voltage V_(REF) is developed at the cathode of diode D5. Voltage VERT1 is coupled via a peak rectifier that includes a diode D6 to a noninverting input terminal of a comparator 72. An inverting input terminal of amplifier 72 is coupled to voltage V_(REF). When signal VERT is at normal operating level, indicating normal vertical deflection, an output voltage V₇₂ of comparator 72 is approximately 12 volts. When vertical deflection fails, output voltage V₇₂ becomes approximately zero volts.

Signal HOR that is indicative of normal horizontal scanning is coupled via a rectifying diode D4 to the emitter of a transistor Q1 of fault detector 70. A capacitor C6 is coupled to the collector of transistor Q1 and to a noninverting input terminal of a comparator 71. The inverting input terminal of comparator 71 is coupled to reference voltage V_(REF) through a voltage divider. When signal HOR is produced, indicating normal horizontal scanning, an output voltage V₇₁ developed at an output terminal 71a of comparator 71 is greater than approximately +12 volts. On the other hand, when signal HOR is missing, and is indicative of a loss of horizontal scanning, voltage V₇₁ is approximately zero volts.

Voltages V₇₁ and V₇₂ are coupled to the bases of a pair of transistors Q2 and Q3, respectively. The emitters of transistors Q2 and Q3 are coupled together at a junction terminal 70a. Terminal 70a is coupled via a resistor R10 in parallel with a bypass capacitor C10 to a voltage level +V₃ that is illustratively +12 volts. The collectors of transistors Q2 and Q3 are coupled to ground through corresponding resistors 73 and 74. When either horizontal scan loss or vertical deflection loss occurs, a voltage SWEEP-LOSS, that is close to zero volts, is developed at terminal 70a. During normal operation, voltage SWEEP-LOSS is at approximately +12 volts.

A low level video signal from antenna or other source 8 is provided by a video processor 9 to a kinescope driver stage 55. Video processor 9 includes, for example, conventional video processing stages of a projection television receiver that receive an input signal from antenna or other source 8. Stage 55 includes a common emitter amplifier transistor 50 arranged in a cascode amplifier configuration with a common base amplifier transistor 51. The video signal produced by processing stages 9 is coupled to the base input of transistor 50. Base voltage for transistor 51 at +12 volts is provided through a resistor 25 from voltage SWEEP-LOSS, during normal deflection operation.

A transistor stage identical to the stage including transistor 51 is provided for each of the three CRT's of the projection television system, as shown, each having their emitters coupled to the collector output of an amplifier stage 50, these connections not being shown in detail.

The output circuit of driver stage 55 includes a series arrangement 29 formed by an inductor L1, a diode D10, an inductor L2, a resistor 27 and a resistor 28. Series arrangement 29 forms a collector load at the collector of transistor 51. A high level amplified video signal is developed at the collector of transistor 51. The output circuit of driver stage 55 also includes opposite conductivity type emitter follower transistors 30 and 81 forming a Class B amplifier with base inputs coupled to the collector of transistor 51 across diode D10. The emitter output of transistor 81 is coupled to the emitter output of transistor 30. The high level amplified video signal is coupled from the emitter output of PNP follower transistor 30 or of NPN follower transistor 81, which corresponds to an output terminal of driver stage 55, to a cathode electrode 56 of image reproducing kinescope or CRT 10 via a kinescope arc current limiting resistor 33 and peaking circuitry comprising resistor 35 and inductor 36. A collector resistor 30a coupled to transistor 30 acts as a kinescope arc current limiting resistor.

Kine supply voltage level +V₁ is coupled to a terminal 28a of stage 55, between series arrangement 29 and resistor 34. Voltage level +V₁ is coupled to terminal 28a via a resistor R24 that is coupled to a filter capacitor C8 and via a self biasing diode 60. The purpose of diode 60 is also described in copending application RCA U.S. Ser. No. 516,386, entitled A SELF BIASING PROTECTION ARRANGEMENT FOR A CATHODE RAY TUBE, in the name of John Barrett George, filed concurrently herewith and incorporated by reference herein. An arrangement similar to stage 55, not shown, is provided for each of CRT's 11 and 12.

When, for example, a user turns off the power to the television receiver, such as, for example, by disconnecting mains supply voltage 116, deflection loss occurs and voltage SWEEP-LOSS attains a near zero volt level. Voltage SWEEP-LOSS at near zero volts causing transistor 51 to become nonconductive. As long as voltage level +V₁ is produced (e.g., from stored charge in the receiver's filter capacitor C4, for example) a cathode voltage V_(K) of CRT 10 is maintained at approximately +225 volts (assuming no video signal is now present). A grid voltage V_(G) that is developed at a control grid of CRT 10 is maintained at a voltage that is not more positive than +27 volts. The large voltage difference between the cathode and grid of CRT 10 causes a cut-off condition to occur in CRT 10 in which a beam current i_(BEAM) at the cathode of CRT 10 becomes near zero. Voltage SWEEP-LOSS at zero volts protects CRT 10 against damage to its display screen even if ultor voltage U is sufficiently large to produce a large beam current. This also occurs should a SWEEP-LOSS occur when the television receiver is still turned on.

Assume that, for example, a fault condition occurs when the power to the television receiver is already turned on, or when the user turns off the power to the television receiver, such that voltage level +V₁ becomes substantially smaller than in normal operation such as, for example, zero volts, but ultor voltage U is still at a normal or substantially high level. When, for example, the user turns off the television receiver, horizontal and vertical deflection cease and voltage SWEEP-LOSS becomes zero, as explained before. Consequently, transistors 51 and 30 become nonconductive.

As explained in the above copending application, U.S. Ser. No. 86,030, diode 60 becomes back biased when voltage level +V₁ is substantially smaller than in normal operation and prevents beam current i_(BEAM) from flowing to ground via, for example, capacitor C4 in the supply at terminal 32 (see FIG. 1a). Therefore, beam or cathode current i_(BEAM) charges a cathode electrode capacitance Cp, formed at the cathode of CRT 10, to develop cathode voltage V_(K) at a large magnitude in a self biasing manner. Voltage V_(K) causes CRT 10 to be, advantageously, substantially in cut-off. The result is that beam current i_(BEAM) becomes close to zero in a negative feedback manner. Advantageously, the cathode voltage of CRT 10 can increase quickly because of the small value of cathode electrode capacitance Cp that is in the order of 15 picofarads. Thus, diode 60 produces a high output impedance of video driver stage 55 at the cathode electrode of CRT 10 relative to ground. The high output impedance that is determined by capacitance Cp provides self bias to CRT 10 that tends to cut-off beam current i_(BEAM).

Had capacitors C4 and C8 not been coupled to terminal 28a of stage 55 through a switch such as diode 60, a significant drop in voltage level +V₁ might have caused beam current i_(BEAM) to flow to ground. Current i_(BEAM) could flow through a main current path that includes an emitter-base P-N junction of transistor 81, because of an avalanche or breakdown condition in such P-N junction, and through capacitors C4 and C8, for example, or through any other supply load that is coupled to terminal 32 of capacitor C4. Therefore, the cathode voltage of CRT 10 would have been too small to provide blanking of beam current i_(BEAM). Therefore, a small cathode-grid voltage difference would have been formed in CRT 10 (not taking into account the operation of the protection circuit according to the invention embodied in circuit 777 to be described below). The small cathode-grid voltage difference in CRT 10 would have produced beam current i_(BEAM) that would have caused damage to the screen of CRT 10, when deflection loss occurs. Due to the small value of capacitance Cp, the response time for producing the cut-off condition in CRT 10 is, advantageously, short.

In accordance with an aspect of the invention, a grid biasing and cut-off circuit 777 is provided for additional CRT protection, providing redundancy to the SWEEP-LOSS signal and the circuit including self bias diode 60. Circuit 777 maintains grid voltage V_(G) at about +27 volts during normal operation and causes voltage V_(G) to be at about -200 volts when signal HOR that is indicative of normal horizontal deflection is not generated. Under various fault conditions circuit 777 provides additional protection that is capable of blanking CRT 10.

As explained above, circuitry for protecting the CRT screen during scan loss is especially important in projection television receivers because of their high density beam currents. The circuitry for addressing the problem of CRT screen damage should be redundant such that no one component failure causes the CRT screen to be burned.

There are, however, situations wherein it is important to have additional protection for the CRT screen in the event of a scan loss. For example, when, due to a fault condition, voltage SWEEP-LOSS is not generated at close to zero volts when vertical scan loss occurs. Also, in a situation where a scan loss occurs when one of the video amplifiers, for example one of transistors 51, develops a collector-to-emitter short, the cathode of the CRT may be forced very close to ground, thus producing a beam current at the critical time when deflection loss has occurred. Deflection loss occurs as a result of, for example, the user's turning-off the television receiver.

A circuit 777 of FIG. 1b, embodying an aspect of the invention, having an input coupled from the horizontal deflection stage shown in FIG. 1a and coupled to the supply voltage +V₁ and further having an output coupled to the control grid of the CRT is provided. In particular, a circuit 777 is provided for each of the three CRT's of the projection television receiver, each having their inputs coupled to the signal HOR and being coupled to the supply voltage +V₁ and having an output coupled to the respective CRT grid. The circuit 777 provides a degree of redundancy in those situations in which the SWEEP-LOSS signal might not be adequate to protect the CRT screens when an additional component failure, for example, a video amplifier short, has occurred, in addition to the loss of sweep during receiver turn-off.

Although the circuit according to the invention is shown used in a projection type television receiver having three CRT's, it is, of course, equally applicable in a receiver having only one CRT where high beam currents can cause phosphor damage or deflection loss.

With reference to FIG. 1b, the signal HOR from the horizontal deflection stage shown in FIG. 1a, and which is indicative of normal horizontal deflection operation, is supplied to resistor 100 and series coupled capacitor 102. Signal HOR typically ranges between -5 volts and +25 volts, with +25 volt peaks occurring during the horizontal retract interval and approximately a -5 volt level during the horizontal trace interval. Capacitor 102 serves as a DC blocking AC coupling capacitor for signal HOR and isolates signal HOR from the 225 volts, voltage level +V₁. The resistor 100 is a current limiting resistor to control the large currents that may occur when the 225 volt supply and line HOR have about 2000 volts between them during a kinescope arc. Line HOR is also utilized as the heater supply for the CRT filaments. Capacitor 102 is a coupling capacitor that shifts the DC component from ground level to about 200 volts, as shown by the waveform at the anode of diode 104. Diode 104 serves as a rectifier and peak clamper.

The active component of the deflection loss protection circuit, which may also be referred to as a "grid kicker" circuit, comprises a PNP transistor 106 whose base- emitter junction is biased on during the negative portion of the signal HOR at the junction of capacitor 102 and a resistor 108. Resistor 108 limits the base current to transistor 106. During the transistor on-time, current also flows from the 225 volt supply of voltage level +V₁ through resistor R24 through the emitter-collector junction of transistor 106. A capacitor 110 is charged, advantageously, over only several cycles through transistor 106, zener diode 112, diode 114 and resistor 116. Zene diode 112 clamps the voltage at the CRT grid, in the embodiment shown, to approximately 27 volts maximum during the charging process. After several cycles of signal HOR, the voltage across capacitor 110 obtains a value near 200 volts and the collector voltage of transistor 106 is at +225 volts, approximately. At this point in time, zener diode 112 ceases conduction because the voltage divider comprising resistors 118 and 120 (resistor 116 can be ignored for purposes of the calculation) is selected to provide approximately 25 volts to the CRT grid, an amount less than the zener value of 27 volts. This is done to prevent noise generation in the zener diode during normal receiver operation. The transistor 106 is now saturated so that a collector to emitter voltage of about 0.5 volts is established. A capacitor 122, embodying an aspect of the invention, is provided between the collector and base junction of transistor 106 as a positive feedback Miller device that slows the transistor turn-off by AC coupling the base tightly to the collector. If the collector voltage attempts to decrease, the base is turned on harder preventing the decrease. Capacitor 122 thus prevents transistor 106 from turning off during the positive portion of the HOR waveform but allows transistor 106 to turn off quickly if the HOR waveform is not present.

When transistor 106 turns off, for example, when signal HOR disappears, indicating the loss of horizontal scan, the collector voltage is pulled to ground by resistor 124. Capacitor 110 still has approximately 200 volts across it. The voltage at the CRT grid and the anode of diode 114 tracks the 225 volt change at the collector of transistor 106 and lowers from approximately +25 volts to about -200 volts. Diode 114 is now reversed biased. The CRT grid then gradually increases toward ground at a time constant, in the preferred embodiment, of about 12.7 seconds determined substantially by resistor 120 and capacitor 110. Meanwhile, advantageously, no current is drawn from 225 volt supply of voltage level +V₁ because transistor 106 and the transistors 51 are turned off. The signal SWEEP-LOSS has become approximately zero volts due to the loss of horizontal deflection and there is no current path from the 225 volt supply of voltage level +V₁ to ground now that transistor 106 is also nonconductive. This condition normally, advantageously, maintains the 225 volt supply on the cathode of the CRT until the filter capacitor C4 of the 225 volt supply discharges from stray leakage, approximately several seconds. Resistor 116 limits the current in zener diode 112 and diode 114 during kinescope arcs. Capacitor 126 is a video bypass between the CRT cathode circuit and the grid. The combination of capacitor 126, capacitor 110 and capacitor 122 bypass kine arc currents around transistor 106 and protect it from damage.

During a scan loss, the scan loss detectors shown in FIG. 1a will provide a SWEEP-LOSS signal of approximately zero volts when either vertical or horizontal scan loss is detected, as explained before. Transistors 51 normally operate with small base currents and with a base voltage near 12 volts. If a fault such as an open collector occurs in any of the transistors 51, the additional current drawn into the base of the bad transistor will lower the bias to the other two amplifiers and turn them off. Capacitor C10 between the scan loss line and the 12 volt supply is a video bypass for the three grounded base upper cascode amplifiers comprising transistors 51.

In the event that a fault occurs in, for example, the cathode circuitry of any of the CRT's during or prior to a sweep-loss, and in particular, a horizontal sweep-loss, the circuit 777 provides an additional degree of protection. In the event, for example, transistor 51 develops an emitter-collector short, the collector of transistor 51 will approach ground level, thus driving transistor 30 on and providing a low voltage at the cathode of the CRT. With a grid voltage of approximately 25 volts and a cathode voltage near ground, a high beam current will be developed. Due to the loss of horizontal sweep, during the receiver turn-off period, a vertical line may be developed near the center of the CRT screen, causing a burned phosphor, if the circuit 777 were not provided. Circuit 777, however, prevents any damage to the CRT screen, because as soon as horizontal deflection ceases, signal HOR ceases to be provided to the base of transistor 106. The loss of signal HOR turns transistor 106 off, and couples the positively charged terminal of capacitor 110 to ground through resistor 124. Accordingly, the negatively charged terminal of capacitor 110, which is coupled to the CRT grid through resistor 128, approaches approximately -200 volts with respect to ground. Prior to horizontal sweep-loss, the negative terminal of capacitor 110 had been at approximately +25 volts with respect to ground. Accordingly, the grid of the CRT is biased sufficiently negatively to cut off the CRT and prevent any beam current from flowing, therefore protecting the CRT phosphor from any damage.

The CRT protection circuit 777 is advantageous in a number of respects. The use of PNP transistor 106 means that the transistor is turned off when horizontal deflection loss occurs, meaning that the charge on capacitor 110 can be maintained for a relatively long period of time depending upon the value of resistor 120. In the embodiment show, the time constant is approximately 12.7 seconds and at one R-C time constant, the grid is still maintained at about -80 volts.

PNP transistor 106 is off during the time that capacitor 110 is maintains the grid at a substantially negative voltage. Therefore, advantageously, there is very little load on the 225 volt supply of voltage level +V₁ during the time that the grid is maintained at a substantially negative voltage. If only a horizontal deflection loss occurs, without a fault in the cathode circuitry, the transistor 106 is turned off as well as the transistors 51 in the video amplifier circuitry due to the loss of sweep. There is no path to ground for the 225 volt supply which makes the 225 volt supply discharge time constant several seconds.

The protection circuit 777 is simple design, having only one active device, transistor 106. No other active devices are necessary, and the circuit need only be coupled to one supply voltage, the 225 volt supply of voltage level +V₁ and does not require any other low voltage supplies in order to operate since it is controlled directly by signal HOR.

The use of Miller capacitance 122 simplifies the horizontal pulse detection. Capacitor 122 is used to keep transistor 106 in saturation during the retrace pulse portion of the horizontal waveform HOR. The non-Miller RC product of capacitor 122 and resistor 124 is approximately 1.6 microseconds. The transistor current gain, or β, of transistor 106 exceeds 50, giving a minimum Miller time constant of 280 microseconds, in the embodiment shown. This gives less than 1/100 time constant of collector voltage sag during retrace and a PNP turn-off time of less than 10 horizontal lines when horizontal sweep is lost. Accordingly, the use of Miller capacitance 122 simplifies the task of sensing the presence of signal HOR and at the same time, allows rapid determination that signal HOR is not present, providing rapid blanking of the CRT screen through grid control.

Three circuits 777 are provided. Only one such circuit is shown for one CRT, but a circuit is provided for each of the grids of the other two CRT's 11 and 12, as would be evident to a person of skill in the art.

Another advantage of the protection circuit 777 is that it allows the grid to be maintained at approximately +25 volts during normal operation with respect to ground. Therefore, maximum beam current can be produced without saturating transistor 51. Maximum beam current in a CRT can be produced when the grid voltage level is allowed to approach the cathode voltage level. A more detailed explanation of why biasing the grid voltage at +25 volts is desirable is described in detail in a copending U.S. patent application Ser. No. 515,512 in the names of Gurley et al., entitled VIDEO DISPLAY APPARATUS WITH KINESCOPE SPOT BURN PROTECTION CIRCUIT, filed concurrently herewith and incorporated by reference herein.

It is important in order to prevent CRT damage, that the grid be able to be switched quickly to a high negative voltage in order to cut off beam current in the event of deflection loss. This is achieved in circuit 777 by the zener diode 112 and diode 114 as well as resistors 118 and 120 providing a voltage divider circuit. During initial charging of capacitor 110 through transistor 106, the zener diode 112 is initially conductive, develops a voltage across resistor 118 of approximately +27 volts and allows capacitor 110 to charge quickly. Once the capacitor has charged, however, the zener diode becomes nonconductive because of the selection of the relative values of resistors 118 and 120 of the voltage divider (approximately 25 volts across resistor 118), and the stored charge on capacitor 110 is placed substantially across resistor 120 having a relatively high resistance. When horizontal sweep-loss occurs, within a few cycles of the lost horizontal sweep signal, transistor 106 turns off and the charge stored on capacitor 110 is placed on the grid of the CRT thereby blanking the CRT screen.

Circuit 777 utilizes only the horizontal deflection signal HOR as an input signal instead of the SWEEP-LOSS signal from the scan loss detection circuit. Whereas, the SWEEP-LOSS signal is produced when either horizontal or vertical scan loss occurs. In addition to providing a degree of redundancy, this is also important in a situation where a fault occurs in both the video amplifier circuitry and the vertical deflection circuitry.

Assume that a vertical deflection loss occurs, and one of the video amplifier transistors 51 shorts. As explained before, beam current can flow, in the absence of circuit 777, to ground through the cathode circuitry, including the failed transistor 51. Should a vertical sweep-loss occur, the faulty transistor 51 will allow beam current to flow to ground. If a circuit similar to circuit 777 was provided to develop a sufficiently large negative voltage at the grid of the CRT when vertical scan loss occurred, and such circuit operated from a signal similar to the SWEEP-LOSS signal developed in the circuit of FIG. 1a that is generated when either loss of vertical or loss of horizontal deflection occurs (instead of only from the signal HOR), and if a capacitor similar to capacitor 110 was charged in order to develop this sufficiently large negative voltage, then the charge on the capacitor would dissipate after a short interval of several time constants. This is so because loss of vertical deflection would have caused the capacitor to discharge. Therefore, the horizontal line would appear on the CRT screen after several time constants. When, subsequently, a user turns off the television receiver (typically a horizontal line does not cause phosphor burn as rapidly as a vertical line or spot), and then the horizontal sweep disappears, because the capacitor that is similar to capacitor 110 is already discharged, a negative voltage at the control grid can no longer be generated. Therefore, a beam spot will be formed at the center of the screen for a brief instant in time, which is often enough to cause CRT phosphor damage at the spot.

This problem is solved by utilizing the horizontal sweep signal HOR instead as a signal such as the SWEEP-LOSS signal as the input to the circuit 777. Should a vertical sweep-loss occur at the same time that one of the video amplifier transistors is shorted, the CRT screen would collapse to a horizontal line, since horizontal sweep is assumed to be maintained. When the user turns off the television receiver, because of, for example, noticing the defect, loss of horizontal deflection signal HOR will turn off transistor 106, placing the negative voltage on capacitor 110 on the grid of the CRT, preventing beam current flow and therefore preventing a spot from appearing at the center of the CRT screen, despite the fact that the horizontal field has collapsed. 

What is claimed is:
 1. A circuit for protecting a cathode ray tube screen from damage by an electron beam emitted by the cathode of the tube, comprising:switch means having a control input responsive to a signal that is indicative of when electron beam current cut-off is required and related to a deflection signal for the electron beam for conducting a current through said switch means when the electron beam current cut-off is not required and for disabling conduction of said current when the electron beam current cut-off is required, said switch means being coupled to a source of a voltage supply; and charge storage means coupled to said switch means and to a control grid of said cathode ray tube for storing a charge therein to develop an electron beam blanking voltage on said charged storage means, said charge storage means being charged from said current that flows through said switch means and that is supplied by said source of said voltage supply when said deflection signal is present at the control input of said switch means; said switch means decoupling said source of said supply voltage from said charge storage means and placing said blanking voltage developed on said charge storage means across said control grid when said signal related to said deflection signal is not present to cut-off the electron beam current in said cathode ray tube.
 2. The circuit recited in claim 1, wherein said signal related to a deflection signal comprises a signal representing a horizontal line deflection signal for the electron beam.
 3. The circuit recited in claim 1, wherein said switch means comprises a PNP transistor having a base coupled to a source of said signal related to a deflection signal for the electron beam and a collector coupled to said charge storage means.
 4. The circuit recited in claim 3, wherein said charge storage means comprises a capacitor and said blanking voltage developed on said charge storage means and applied to said grid comprises a negative voltage.
 5. The circuit recited in claim 4, further comprising means for charging said charge storage means through said switch means and for holding a voltage level on said grid substantially equal to a bias level on a cathode of said cathode ray tube when said signal related to said deflection signal is present at said switch means.
 6. The circuit recited in claim 5, wherein said means for charging and holding comprises an avalanche device coupling a negative terminal of said charge storage means to ground and a voltage divider comprising a first resistor connected across said charge storage means coupled in series with a second resistor coupled across said avalanche device.
 7. The circuit recited in claim 5, wherein said first resistor provides said charge storage means with a discharge time constant of approximately 10 seconds.
 8. The circuit recited in claim 1, further comprising means for detecting loss of either or both vertical and horizontal deflection signals, said means for detecting being coupled to kine driver means for said cathode ray tube to provide a blanking level to the cathode of said cathode ray tube to suppress electron beam current.
 9. The circuit recited in claim 1, further comprising a diode coupled between said cathode ray tube cathode and the supply voltage for self biasing said cathode to a blanking voltage to suppress electron beam current in the event of failure of said supply voltage.
 10. The circuit recited in claim 3, wherein said signal related to a deflection signal is related to a horizontal deflection signal and further comprising a feedback path coupled between said base and collector of said PNP transistor to provide positive feedback holding said PNP transistor in a conductive state during a trace interval of said signal related to a horizontal deflection signal.
 11. The circuit recited in claim 10, wherein said feedback path includes a capacitance.
 12. The circuit recited in claim 1, wherein said switch means is coupled only to one said supply voltage.
 13. A circuit for protecting a cathode ray tube screen from damage by an electron beam emitted by the cathode of the tube comprising:switch means having a control input responsive to a signal related to a horizontal deflection signal for the electron beam, said switch means having a conductive state for conducting a current therethrough when electron beam current cut-off is not required and a nonconductive state for disabling conduction of said current when the electron beam current cut-off is required, said switch means being coupled to a source of a voltage supply; and charge storage means coupled to said switch means and to a control grid of said cathode ray tube for storing a charge therein to develop an electron beam blanking voltage on said charge storage means, said charge storage means being charged from said current that flows through said switch means, and supplied by said source of said voltage supply when the signal related to the horizontal deflection signal is present, the conduction state of the switch means being controlled by said signal related to the horizontal deflection signal; said switch means placing said blanking voltage developed on said charge storage means across said control grid when said signal related to a horizontal deflection signal is at a state indicating improper horizontal deflection to cut-off electron beam current in said cathode ray tube.
 14. The circuit recited in claim 13, wherein said switch means is conductive when said signal related to a horizontal deflection signal is present and becomes nonconductive when said signal related to a horizontal deflection signal is not present.
 15. The circuit recited in claim 14, wherein the charge storage means is charged through said switch means when said signal related to a horizontal deflection signal is present.
 16. The circuit recited in claim 15, wherein said switch means comprises a PNP transistor having a base coupled to a source of said signal related to a horizontal deflection signal for the electron beam and a collector coupled to said charge storage means.
 17. The circuit recited in claim 13, wherein said charge storage means comprises a capacitor and said blanking voltage developed on said charge storage means and applied to said grid comprises a negative voltage.
 18. The circuit recited in claim 17, further comprising means for charging said charge storage means and for holding a voltage level on said grid substantially equal to a bias level on a cathode of said cathode ray tube when said signal related to said deflection signal is present at said switch means.
 19. The circuit recited in claim 18, wherein said means for charging and holding comprises an avalanche device coupling a negative terminal of said charge storage means to ground and a voltage divider comprising a first resistor connected across said charge storage means coupled in series with a second resistor coupled across said avalanche device.
 20. The circuit recited in claim 19, wherein said means for charging and holding charges said charge storage means through said switch means.
 21. The circuit recited in claim 19, wherein said first resistor provides said charge storage means with a discharge time constant of approximately 10 seconds.
 22. The circuit recited in claim 13, further comprising means for detecting loss of either or both vertical and horizontal deflection signals, said means for detecting being coupled to kine driver means for said cathode ray tube to provide a blanking level to the cathode of said cathode ray tube to suppress electron beam current.
 23. The circuit recited in claim 13, further comprising a diode coupled between said cathode ray tube cathode and the supply voltage for self biasing said cathode to a blanking voltage to suppress electron beam current in the event of failure of said supply voltage.
 24. The circuit recited in claim 16, further comprising a feedback path coupled between said base and collector of said PNP transistor to provide positive feedback holding said PNP transistor in a conductive state during a trace interval of said signal related to a horizontal deflection signal.
 25. The circuit recited in claim 24, wherein said feedback path includes a capacitance.
 26. The circuit recited in claim 13, wherein said switch means is coupled only to one said supply voltage.
 27. A circuit for protecting a cathode ray tube screen from damage by an electron beam emitted by the cathode of the tube comprising:switch means having a control input responsive to a signal related to a horizontal deflection signal for the electron beam, said switch means having a conductive state for conducting a current therethrough when electron beam current cut-off is not required and a nonconductive state for disabling conduction of said current when the electron beam current cut-off is required, said switch means being coupled to a source of a supply voltage supply; and charge storage means coupled to said switch means and to a control grid of said cathode ray tube, said charge storage means being charged from said current that flows through said switch means and supplied by said voltage supply when the signal related to the horizontal deflection signal is present, the conduction state of the switch means being controlled by said signal related to the horizontal deflection signal, said switch means being conductive when said signal related to the horizontal deflection signal is present and being nonconductive when said signal related to the horizontal deflection signal is not present; said switch means placing a blanking voltage developed on said charge storage means across said control grid when said signal related to the horizontal deflection signal is at a state indicating improper horizontal deflection to cut-off electron beam current in said cathode ray tube.
 28. The circuit recited in claim 27, wherein said switch means comprises a PNP transistor having a base coupled to a source of said signal related to a horizontal deflection signal for the electron beam and a collector coupled to said charge storage means.
 29. The circuit recited in claim 27, wherein said charge storage means comprises a capacitor and said blanking voltage developed on said charge storage means and applied to said grid comprises a negative voltage.
 30. The circuit recited in claim 29, further comprising means for charging said charge storage means through said switch means and for holding a voltage level on said grid substantially equal to a bias level on a cathode of said cathode ray tube when said signal related to said deflection signal is present at said switch means.
 31. The circuit recited in claim 30, wherein said means for charging and holding comprises an avalanche device coupling a negative terminal of said charge storage means to ground and a voltage divider comprising a first resistor connected across said charge storage means coupled in series with a second resistor coupled across said avalanche device.
 32. The circuit recited in claim 31, wherein said first resistor provides said charge storage means with a discharge time constant of approximately 10 seconds.
 33. The circuit recited in claim 27, further comprising means for detecting loss of either or both vertical and horizontal deflection signals, said means for detecting being coupled to kine driver means for said cathode ray tube to provide a blanking level to the cathode of said cathode ray tube to suppress electron beam current.
 34. The circuit received in claim 27, further comprising a diode coupled between said cathode ray tube cathode and the supply voltage for self biasing said cathode to a blanking voltage to suppress electron beam current in the event of failure of said supply voltage.
 35. The circuit recited in claim 28, further comprising a feedback path coupled between said base and collector of said PNP transistor to provide positive feedback holding said PNP transistor in a conductive state during a trace interval of said signal related to a horizontal deflection signal.
 36. The circuit recited in claim 35, wherein said feedback path includes a capacitance.
 37. The circuit recited in claim 27, wherein said switch means is coupled only to one said supply voltage.
 38. A video display apparatus for protecting a cathode ray tube screen from damage by an electron beam emitted from a cathode electrode of said cathode ray tube, comprising:means for generating a control signal that is indicative when normal operation is required and when a cut-off of an electron beam current in said cathode ray tube is required; a capacitor coupled to a control grid electrode of said cathode ray tube; means coupled to said capacitor for developing in said capacitor a first voltage during normal operation; a source of a supply, second voltage; and a switch responsive to said control signal and coupled to said source of said second voltage and to said capacitor for coupling said second voltage to said capacitor through said switch at a conductive state of said switch to develop a grid voltage at said grid electrode at a first magnitude in accordance with said first and second voltages when beam current cut-off is not required and for decoupling said source of said second voltage from said capacitor at a nonconductive state of said switch such that said first voltage is developed at said grid electrode at a second magnitude that provides the beam current blanking when said electron beam current cut-off is required. 